Continuous-wave radar

Change of wavelength caused by motion of the source

This kind of radar can cost less than $10 (2021). Return frequencies are shifted away from the transmitted frequency based on the Doppler effect when objects are moving. There is no way to evaluate distance. This type of radar is typically used with competition sports, like golf, tennis, baseball, NASCAR racing, and some smart-home appliances including light-bulbs and motion sensors.

The Doppler frequency change depends on the speed of light in the air (c’ ≈ c/1.0003 is slightly slower than in vacuum) and v the speed of the target:[4]

${\displaystyle f_{r}=f_{t}\left({\frac {1+v/c'}{1-v/c'}}\right)}$

The Doppler frequency is thus:[5]

${\displaystyle f_{d}=f_{r}-f_{t}=2v{\frac {f_{t}}{c'-v}}}$

Since the usual variation of targets' speed of a radar is much smaller than ${\displaystyle c',(v\ll c')}$, it is possible to simplify with ${\displaystyle c'-v\approx c'}$ :

${\displaystyle f_{d}\approx 2v{\frac {f_{t}}{c'}}}$

Continuous-wave radar without frequency modulation (FM) only detects moving targets, as stationary targets (along the line of sight) will not cause a Doppler shift. Reflected signals from stationary and slow-moving objects are masked by the transmit signal, which overwhelms reflections from slow-moving objects during normal operation.

Frequency-modulated continuous-wave radar (FM-CW) – also called continuous-wave frequency-modulated (CWFM) radar[6] – is a short-range measuring radar set capable of determining distance. This increases reliability by providing distance measurement along with speed measurement, which is essential when there is more than one source of reflection arriving at the radar antenna. This kind of radar is often used as "radar altimeter" to measure the exact height during the landing procedure of aircraft.[7] It is also used as early-warning radar, wave radar, and proximity sensors. Doppler shift is not always required for detection when FM is used. While early implementations, such as the APN-1 Radar Altimeter of the 1940s, were designed for short ranges, Over The Horizon Radars (OTHR) such as the Jindalee Operational Radar Network (JORN) are designed to survey intercontinental distances of some thousands of kilometres.

In this system the transmitted signal of a known stable frequency continuous wave varies up and down in frequency over a fixed period of time by a modulating signal. Frequency difference between the receive signal and the transmit signal increases with delay, and hence with distance. This smears out, or blurs, the Doppler signal. Echoes from a target are then mixed with the transmitted signal to produce a beat signal which will give the distance of the target after demodulation.

A variety of modulations are possible, the transmitter frequency can slew up and down as follows :

• Sine wave, like air raid siren
• Sawtooth wave, like the chirp from a bird
• Triangle wave, like police siren in the United States
• Square wave, like police siren in the United Kingdom

Range demodulation is limited to 1/4 wavelength of the transmit modulation. Instrumented range for 100 Hz FM would be 500 km. That limit depends upon the type of modulation and demodulation. The following generally applies.

${\displaystyle {\text{Instrumented Range}}=F_{r}-F_{t}={\frac {\text{Speed of Light}}{(4\times {\text{Modulation Frequency}})}}}$

The radar will report incorrect distance for reflections from distances beyond the instrumented range, such as from the moon. FMCW range measurements are only reliable to about 60% of the instrumented range, or about 300 km for 100 Hz FM.

Ranging with an FM-CW radar system: if the error caused by a possible Doppler frequency ${\displaystyle f_{D}}$ can be ignored and the transmitter's power is linearly frequency modulated, then the time delay (${\displaystyle \Delta t}$) is proportional to the difference of the transmitted and the received signal (${\displaystyle \Delta f}$) at any time.

Sawtooth modulation is the most used in FM-CW radars where range is desired for objects that lack rotating parts. Range information is mixed with the Doppler velocity using this technique. Modulation can be turned off on alternate scans to identify velocity using unmodulated carrier frequency shift. This allows range and velocity to be found with one radar set. Triangle wave modulation can be used to achieve the same goal.

As shown in the figure the received waveform (green) is simply a delayed replica of the transmitted waveform (red). The transmitted frequency is used to down-convert the receive signal to baseband, and the amount of frequency shift between the transmit signal and the reflected signal increases with time delay (distance). The time delay is thus a measure of the range; a small frequency spread is produced by nearby reflections, a larger frequency spread corresponds with more time delay and a longer range.

With the advent of modern electronics, digital signal processing is used for most detection processing. The beat signals are passed through an analog-to-digital converter, and digital processing is performed on the result. As explained in the literature, FM-CW ranging for a linear ramp waveform is given in the following set of equations:[7]

${\displaystyle k={\frac {\Delta {f_{radar}}}{\Delta {t_{radar}}}}}$

where ${\displaystyle \Delta {f_{radar}}}$ is the radar frequency sweep amount and ${\displaystyle \Delta {t_{radar}}}$ is the time to complete the frequency sweep.

Then, ${\displaystyle \Delta {f_{echo}}=t_{r}k}$, rearrange to a more useful:

${\displaystyle t_{r}={\frac {\Delta {f_{echo}}}{k}}}$, where ${\displaystyle t_{r}}$ is the round trip time of the radar energy.

It is then a trivial matter to calculate the physical one-way distance for an idealized typical case as:

${\displaystyle {\text{dist}}_{oneway}={\frac {c't_{r}}{2}}}$

where ${\displaystyle c'=c/n}$ is the speed of light in any transparent medium of refractive index n (n=1 in vacuum and 1.0003 for air).

For practical reasons, receive samples are not processed for a brief period after the modulation ramp begins because incoming reflections will have modulation from the previous modulation cycle. This imposes a range limit and limits performance.

${\displaystyle {\text{Range Limit}}=0.5\ c'\ t_{radar}}$

Sinusoidal FM modulation identifies range by measuring the amount of spectrum spread produced by propagation delay (AM is not used with FMCW).

Sinusoidal FM is used when both range and velocity are required simultaneously for complex objects with multiple moving parts like turbine fan blades, helicopter blades, or propellers. This processing reduces the effect of complex spectra modulation produced by rotating parts that introduce errors into range measurement process.

This technique also has the advantage that the receiver never needs to stop processing incoming signals because the modulation waveform is continuous with no impulse modulation.

Sinusoidal FM is eliminated by the receiver for close in reflections because the transmit frequency will be the same as the frequency being reflected back into the receiver. The spectrum for more distant objects will contain more modulation. The amount of spectrum spreading caused by modulation riding on the receive signal is proportional to the distance to the reflecting object.

The time domain formula for FM is:

${\displaystyle y(t)=\cos \left\{2\pi [f_{c}+\mathrm {B} \cos \left(2\pi f_{m}t\right)]t\right\}\,}$

where ${\displaystyle \mathrm {B} ={\frac {f_{\Delta }}{f_{m}}}}$ (modulation index)

A time delay is introduced in transit between the radar and the reflector.

${\displaystyle y(t)=\cos \left\{2\pi [f_{c}+\mathrm {B} \cos \left(2\pi f_{m}(t+\delta t)\right)](t+\delta t)\right\}\,}$

where ${\displaystyle \delta t=}$ time delay

The detection process down converts the receive signal using the transmit signal. This eliminates the carrier.

${\displaystyle y(t)=\cos \left\{2\pi [f_{c}+\mathrm {B} \cos \left(2\pi f_{m}(t+\delta t)\right)](t+\delta t)\right\}\;\cos \left\{2\pi [f_{c}+\mathrm {B} \cos \left(2\pi f_{m}t\right)]t\right\}\,}$

${\displaystyle y(t)\approx \cos \left\{-4t\pi \mathrm {B} \sin(2\pi f_{m}(2t+\delta t)\sin(\pi f_{m}\delta t)+2\delta t\pi \mathrm {B} \cos(2\pi f_{m}(t+\delta t))\right\}\,}$

The Carson bandwidth rule can be seen in this equation, and that is a close approximation to identify the amount of spread placed on the receive spectrum:

${\displaystyle {\text{Modulation Spectrum Spread}}\approx 2(\mathrm {B} +1)f_{m}\sin(\delta t)}$

${\displaystyle {\text{Range}}=0.5C/\delta t}$

Receiver demodulation is used with FMCW similar to the receiver demodulation strategy used with pulse compression. This takes place before Doppler CFAR detection processing. A large modulation index is needed for practical reasons.

Practical systems introduce reverse FM on the receive signal using digital signal processing before the fast Fourier transform process is used to produce the spectrum. This is repeated with several different demodulation values. Range is found by identifying the receive spectrum where width is minimum.

Practical systems also process receive samples for several cycles of the FM in order to reduce the influence of sampling artifacts.

The radar receive antenna is located nearby the radar transmit antenna in monostatic radar.

Feed-through null is typically required to eliminate bleed-through between the transmitter and receiver to increase sensitivity in practical systems. This is typically used with continuous-wave angle tracking (CWAT) radar receivers that are interoperable with surface-to-air missile systems.

Interrupted continuous-wave can be used to eliminate bleed-through between the transmit and receive antenna. This kind of system typically takes one sample between each pair of transmit pulses, and the sample rate is typically 30 kHz or more. This technique is used with the least expensive kinds of radar, such as those used for traffic monitoring and sports.

FM-CW radars can be built with one antenna using either a circulator, or circular polarization.

The radar receive antenna is located far from the radar transmit antenna in bistatic radar. The transmitter is fairly expensive, while the receiver is fairly inexpensive and disposable.

This is typically used with semi-active radar homing including most surface-to-air missile systems. The transmit radar is typically located near the missile launcher. The receiver is located in the missile.

The transmit antenna illuminates the target in much the same way as a search light. The transmit antenna also issues an omnidirectional sample.

The receiver uses two antennas – one antenna aimed at the target and one antenna aimed at the transmit antenna. The receive antenna that is aimed at the transmit antenna is used to develop the feed-through null, which allows the target receiver to operate reliably in or near the main beam of the antenna.

The bistatic FM-CW receiver and transmitter pair may also take the form of an over-the-air deramping (OTAD) system. An OTAD transmitter broadcasts an FM-CW signal on two different frequency channels; one for synchronisation of the receiver with the transmitter, the other for illuminating the measurement scene. Using directive antennas, the OTAD receiver collects both signals simultaneously and mixes the synchronisation signal with the downconverted echo signal from the measurement scene in a process known as over-the-air deramping. The frequency of deramped signal is proportional to the bistatic range to the target less the baseline distance between the OTAD transmitter and the OTAD receiver.[8]

Most modern systems FM-CW radars use one transmitter antenna and multiple receiver antennas. Because the transmitter is on continuously at effectively the same frequency as the receiver, special care must be exercised to avoid overloading the receiver stages.

Monopulse antennas produce angular measurements without pulses or other modulation. This technique is used in semi-active radar homing.

The transmit signal will leak into the receiver on practical systems. Significant leakage will come from nearby environmental reflections even if antenna components are perfect. As much as 120 dB of leakage rejection is required to achieve acceptable performance.

Three approaches can be used to produce a practical system that will function correctly.

• Null
• Filter
• Interruption

Null and filter approaches must be used with bistatic radar, like semi-active radar homing, for practical reasons because side-lobes from the illumination radar will illuminate the environment in addition to the main-lobe illumination on the target. Similar constraints apply to ground-based CW radar. This adds cost.

Interruption applies to cheap hand held mono-static radar systems (police radar and sporting goods). This is impractical for bistatic systems because of the cost and complexity associated with coordinating time with nuclear precision in two different locations.

The design constraint that drives this requirement is the dynamic range limitation of practical receiver components that include band pass filters that take time to settle out.

The null approach takes two signals:

• A sample of the transmit signal leaking into the receiver
• A sample of the actual transmit signal

The actual transmit signal is rotated 180 degrees, attenuated, and fed into the receiver. The phase shift and attenuation are set using feedback obtained from the receiver to cancel most of the leakage. Typical improvement is on the order of 30 dB to 70 dB.

The filter approach relies on using a very narrow band reject filter that will eliminate low velocity signals from nearby reflectors. The band reject area spans 10 mile per hour to 100 mile per hour depending upon the anticipated environment. Typical improvement is on the order of 30 dB to 70 dB.

While interrupted carrier systems are not considered to be CW systems, performance characteristics are sufficiently similar to group interrupted CW systems with pure CW radar because the pulse rate is high enough that range measurements cannot be done without frequency modulation (FM).

This technique turns the transmitter off for a period before receiver sampling begins. Receiver interference declines by about 8.7 dB per time constant. Leakage reduction of 120 dB requires 14 recover bandwidth time constants between when the transmitter is turned off and receiver sampling begins.

The interruption concept is widely used, especially in long-range radar applications where the receiver sensitivity is very important. It is commonly known as "frequency modulated interrupted continuous wave", or FMICW.